Apparatus for transmitting digital information using electromagnetic waves, data transmission apparatus, and method

ABSTRACT

An apparatus is provided for generating a transmission wave. The apparatus includes a plurality of antennas and a plurality of signal generators. The plurality of antennas has polarization diversity. The plurality of signal generators are each coupled to one of the antennas and configured to generate a continuous twisted wave by driving each of the antennas using independent, coordinated, and distinct sinusoidal waves, and having a twist frequency and a carrier frequency, the twist frequency lower than the carrier frequency. A method is also provided.

CROSS REFERENCE TO RELATED APPLICATION

This application is a continuation of and claims priority to U.S. patentapplication Ser. No. 15/892,939, which was filed on Feb. 9, 2018, nowU.S. Pat. No. 10,804,997, issued Oct. 12, 2020, which claims the benefitof U.S. Provisional Application Ser. No. 62/457,758, which was filed onFeb. 10, 2017, the disclosures of which are hereby incorporated byreference.

TECHNICAL FIELD

Examples disclosed herein are generally related to wireless informationtransmission and reception, and more particularly related to systems andmethods for communicating digital information over radio frequency wavesand detection and manipulation of substance using radio waves.

BACKGROUND OF THE DISCLOSURE

It was previously known to use radio wave communication with crosseddipoles to communicate from sensors in corn fields to collectionstations, as shown in U.S. Pat. Nos. 6,271,790; 6,204,810; and6,570,536. This prior effort is known as eSpin. The lower powerrequirement and better penetration was validated in this practicalapplication. During prototype testing of this communications system, twomajor findings occurred. First, there was an observed 30 dB to 42 dBimprovement in signal selectivity out of noise. This finding wasmeasured, but not understood. Secondly, using different spinfrequencies, three or more streams of video could be multiplexed on thesame frequency range, but on de-spin the streams were merged together.The wave suppressed the carrier and communicated on both side bands.This produced a ribbon in three dimensions that communicated over a widefrequency spectrum. The wide spectrum of frequencies used by suchtechnique is not compatible with the way the FCC allocates frequencyspectrum and may interfere with legacy radio waves.

It was also previously known to use radio wave communication using atwisted wave technology with Orbital Angular Momentum (OAM), as shown inU.S. Pat. No. 9,853,799. Such twisted wave technology depends on thedifferent shape of the wave front to encode data. However, OAM does notregister on normal radio devices. These waves are not visible to normalmethods which are based upon sinusoidal waves that register on a FastFourier Transform (FFT). OAM requires very specialized equipment fortransmission and reception and with only a small antenna misalignment,the reception fails. The wide spectrum of frequencies used by OAM is notcompatible with the way the FCC allocates frequency spectrum and mayinterfere with legacy radio waves.

Further previously known techniques involve narrow bandingcommunication. In one early form, radio narrow band communication wasdone with Continuous Wave (CW) communication of Morse code. It waslimited in speed by the human operator's ability to receive and recordthe Morse code encoded information. Typically a maximum of 18 to 20words per minute was communicated. It is characterized as on off keying(OOK) which is limited in speed since side bands are created when thesignal is turned on and off rapidly. In another form, radio teletype(RTTY) provided digital communication which communicated “mark” and“space” information encoded in two different analog tones which usedSingle Side Band (SSB) to transmit the two audio tones to produceaudio-frequency shift keying (AFSK). At this point the communication wasno longer narrow band. The changes in tones or frequencies created sideband noise. The next effort was Gaussian frequency-shift keying (GFSK)which made transitions smoother, reduced the required power, and reducedintersymbol interference. The next effort to reduce side band creationwas Minimum-shift keying (MSK) which reduced the frequency differencebetween the “mark” and “space” frequencies. That was then improved toGaussian minimum shift keying (GMSK) which smoothed the transitionbetween the frequencies and is used in Global System for MobileCommunications (GSM) for cellular phone technology.

Management techniques are also previously known. Cellular networkscurrently provide service to a portion of the world's population usingvery limited radio frequency resources. There exists a need forconsistent reliable secure service for both cell phones and ruralInternet, and there is a growing need for enhanced service capabilitiesdue to the advent of self-driving vehicles.

Detection of substances has previously been done using radio waves basedupon the nucleus spin change for nitrogen in a magnetic field, in somecases the earth's magnetic field. This radio frequency range ended up inthe AM radio band and turned out to be of limited value. The rotationaland vibrational frequencies of some substances are known and used, suchas water's natural vibration frequency (about 2.4 GHz), and thesevibration frequencies make a microwave oven work. However, the use ofradio frequency substance detection has been very limited. In the radiofrequency range from a 10 kHz to 100 GHz, there are so many excitationfrequency lines that the normal methods for using them to distinguishsubstances are not practical. Accordingly, there exists a need forfurther improvements.

SUMMARY

An apparatus and method are provided for generating and capturing atransmission wave, and an apparatus and method are provided fortransmitting and receiving digital information. The apparatus and methodcan be implemented to ultra-narrow band communication, communicationmanagement, and substance detection and manipulation.

According to one aspect, an apparatus is provided for generating atransmission wave. The apparatus includes a plurality of antennas and aplurality of signal generators. The plurality of antennas haspolarization diversity. The plurality of signal generators are eachcoupled to one of the antennas and configured to generate a continuoustwisted wave by driving each of the antennas using independent,coordinated, and distinct sinusoidal waves, and having a twist frequencyand a carrier frequency, the twist frequency lower than the carrierfrequency.

According to another aspect, an apparatus is provided for capturing atransmission wave. The apparatus includes a plurality of antennas and aplurality of fast fourier transform (FFT) analyzers. The plurality ofantennas has polarization diversity. The plurality of fast fouriertransform (FFT) analyzers are each coupled to one of the antennas, theantennas configured to capture a continuous twisted wave by driving eachof the antennas using independent, coordinated, and distinct sinusoidalwaves, and having a twist frequency and a carrier frequency, the twistfrequency lower than the carrier frequency.

According to yet another aspect, an apparatus is provided fortransmitting digital information. The apparatus includes a plurality ofantennas and a plurality of signal generators. The plurality of antennashas polarization diversity. The plurality of signal generators is eachcoupled to one of the antennas and configured to: a) drive the antennasto generate a transmission wave comprising a continuous twisted wavehaving a carrier frequency and a twist frequency lower than the carrierfrequency; and b) encode digital information on the continuous twistedwave by shifting the carrier wave between a first carrier frequency anda second carrier frequency.

According to even another aspect, an apparatus is provided for receivingdigital information. The apparatus includes a plurality of antennas anda plurality of signal receivers. The plurality of antennas haspolarization diversity. The plurality of signal receivers each has anFFT processor, each signal receiver coupled to one of the antennas, theplurality of antennas and signal receivers configured to receive acaptured wave comprising a continuous twisted wave having a carrierfrequency and a twist frequency lower than the carrier frequency as anoutput signal from each of the antennas to decode digital information onthe continuous twisted wave in the form of shifts between a firstcarrier frequency and a second carrier frequency.

According to a further aspect, a method is provided for creating atransmission wave. The method includes: providing a plurality ofantennas having polarization diversity between the antennas; andgenerating a continuous twisted wave having a twist frequency and acarrier frequency, the twist frequency lower than the carrier frequency,by driving each of the antennas using independent, coordinated, andsinusoidal waves.

According to a yet even further aspect, a method is provided fortransmitting digital information. The method includes: generating atransmission wave comprising a continuous twisted wave having a carrierfrequency and a twist frequency lower than the carrier frequency; andencoding digital information on the continuous twisted wave by shiftingthe carrier frequency between a first carrier frequency and a secondcarrier frequency; wherein shifting comprises smoothly transitioningbetween the first carrier frequency and the second carrier frequencywith phase adjustment in a manner that maintains power transition suchthat as one of the first and second frequencies drops power to zeroanother of the first and second frequencies brings its power up so thatthe total power stays the same.

BRIEF DESCRIPTION OF THE DRAWINGS

Exemplary embodiments of the various disclosures are described belowwith reference to the following accompanying drawings. The drawings maybe considered to represent scale.

FIG. 1 shows the block diagram of a potential apparatus used to send andreceive data communicating with CTwists waves;

FIG. 2 is the list of formulas used to create circular, “SuperCircular”, CTwists, and “Complex CTwists” waves;

FIG. 3 is an end view of a three-dimensional digitally encoded radiofrequency (CTwists) wave generated by a crossed dipole antenna;

FIG. 4 is a side view of the CTwists wave;

FIG. 5 is a top view of the CTwists wave;

FIG. 6 is a three-dimensional front perspective view from above of theCTwists wave;

FIG. 7 is a sample Fast Fourier Transform (FFT) of the CTwists wave ofFIGS. 3-6;

FIG. 8 is a representation of a cross dipole antenna system configuredto generate and receive the CTwists wave of FIGS. 3-6;

FIG. 9 is a view of a three crossed dipole antenna configured totransmit and receive the CTwists wave of FIGS. 10-13;

FIG. 10 is a front end view of the wave produced from 3 orthogonalantennas depicted in FIG. 9;

FIG. 11 is a side view of the wave produced from 3 orthogonal antennas;

FIG. 12 is a top view of the wave produced from 3 orthogonal antennas;

FIG. 13 is a three-dimensional front perspective view from above of theCTwists wave produced from 3 orthogonal antennas;

FIG. 14 is an end view of a Super Circular wave created using a 3orthogonal antenna set;

FIG. 15 is a front view of a Super Circular wave created using a 3orthogonal antenna set;

FIG. 16 is a top view of a Super Circular wave created using a 3orthogonal antenna set;

FIG. 17 is a 3D view of a Super Circular wave created using a 3orthogonal antenna set;

FIGS. 18A and 18B are outlet end view and side view of a horn threeorthogonal antenna system, and FIG. 18C is a side view of an optionalparabolic three orthogonal antenna system;

FIG. 19 is a schematic block diagram showing notional flow of data in adirect antenna control process for the antenna array depicted in FIGS.18A and 18B;

FIG. 20 is a representation of data communication through a Wobble;

FIG. 21 is a right triangle showing amplitude relationships for smoothtransitions;

FIG. 22 is the FFT of a Wobble;

FIG. 23 is example of reception of Wobble broadcast out of phase;

FIG. 24 is an example of FFT of Wobble broadcast out of phase;

FIG. 25 is example of reception of Wobble broadcast in phase;

FIG. 26 is an example of FFT of Wobble broadcast in phase;

FIG. 27 is a picture of the 802.11n 2.4 GHz spectrum;

FIG. 28 is the table of FFT options;

FIG. 29 is a picture of the CTwists 802.11n 2.4 GHz spectrum;

FIG. 30 is a picture of CTwists data flow;

FIG. 31 is an example of reception of Wobble broadcast with skew drift;

FIG. 32 is an example of simple substance excitation;

FIG. 33 is an example of CTwists simple substance excitation;

FIG. 34 is an example of simple second level substance excitation;

FIG. 35 is an example of CTwists second level substance excitation;

FIGS. 36A and 36B are a front view and a side view of an example portalsubstance detection system;

FIG. 37 is an example substance detection chamber;

FIGS. 38A and 38B are a side view and a front view of an exampletransmit/receive antenna for either chamber or portal;

FIG. 39 is an example land mine detector; and

FIGS. 40A and 40B are a top view and a front view of an example antennafor the land mine detector.

DETAILED DESCRIPTION OF THE EMBODIMENTS

This disclosure of the invention is submitted in furtherance of theconstitutional purposes of the U.S. Patent Laws “to promote the progressof science and useful arts” (Article 1, Section 8).

The terms “a”, “an”, and “the” as used in the claims herein are used inconformance with long-standing claim drafting practice and not in alimiting way. Unless specifically set forth herein, the terms “a”, “an”,and “the” are not limited to one of such elements, but instead mean “atleast one”.

As used herein, the term CTwists is understood to mean the use of radiowaves twisted at a frequency lower than the carrier frequency createdthrough antennas with polarization diversity and directly driven withseparate electronic sections in coordination.

As used herein, the term eSpin is understood to mean the communicationsystem described in U.S. Pat. Nos. 6,271,790; 6,204,810; and 6,570,536.

As used herein, the term “Super Circular Polarized Waves” is understoodto mean the set of circular and elliptical polarized waves created bythree orthogonal antennas.

As used herein, the term twist (as in twist frequency) is understood tomean the rotation of the carrier frequency one complete rotation or fornon-CTwists waves—it means the average carrier frequency for the subjectfrequency range.

As used herein, the term Wobble is understood to mean a defined set oftwists (in the example herein, it is 32 twists).

As used herein, the term sinusoidal is understood to mean wavesgenerated through combinations of sine and cosine functions.

As used herein, the term Smooth Transition is understood to mean adefined set of twists (in the example herein, it is 4 twists) used as atransition to a new frequency is desired to reduce the power of thecurrent frequency to zero while increasing the target frequency fromzero to the target power level. This is done keeping the total powerlevel constant.

As used herein, the term Skew is understood to mean a time differencefrom the start of a Wobble to the actual Wobble measurement (samplingwindow).

Throughout this disclosure, headings and/or subheadings are provided inthe detailed disclosure for convenience and are not provided forinterpretation.

The present disclosure (CTwists) relates, in general, to digital radiocommunications system and method, namely a system and method forcommunicating digital information over radio frequencies (includingfrequencies from a few KHz to hundreds of GHz) with a decrease powerrequirement, greater distance, greater number of channels, greater datathroughput, and less interference with legacy communication. The CTwistswave shows great promise in detecting and manipulating substances.Analysis of the CTwists Complex Wave projects the following improvementsover the 802.11n 2.4 GHz waves:

TABLE 1 Complex CTwists Wave Attributes Attribute Advantage Source LessPower or 30 to 42 dB eSpin Tests Greater Distance 17 dB Narrow BandModel More Channels 50 Times Narrow Band Model Data Throughput 50 TimesNarrow Band Model Better Penetration 6 Times eSpin Tests LessInterference TBD Wave Analysis

CTwists is a major breakthrough in digital radio communication andsubstance detection and manipulation. CTwists will be explained in thefollowing sections:

I. CTwists Wave Generation

II. Ultra-Narrow Band Communication

III. Special FFT Processing

IV. Communication Management

V. Substance Detection and Manipulation

I. CTwists Wave Generation

CTwists is similar to the prior analog eSpin technology in that botheSpin and the CTwists use radio waves rotated at frequencies lower thanthe carrier's frequency. However, the CTwists differs from eSpin in thateSpin suppressed the carrier (two peaks) and transmits its analog dataover its side bands and CTwists creates almost no side bands andtransmits its digital data using its two carrier peaks. The method ofcreation of the rotated wave and reception of the rotated wave alsodiffer.

CTwists can be advantageously exploited, in general, in all kinds ofradio communication, and in particular, in rural Internet delivery,Wi-Fi, cellular, Internet of Things (IOT), and satellite communications.Furthermore, the present apparatus and method for generating andcapturing a transmission wave, as well as the present apparatus andmethod for transmitting and receiving digital information hasapplication in the fields of substance detection and medical diagnosticsand treatment.

FIG. 1 is a block diagram of an apparatus used to send and receivecommunication using CTwists waves, according to one aspect. An array 10of antennas 12, 14, and 16 with polarization diversity communicates withindividual circulators 20 that are used to isolate, transmit, andreceive signals. A receive down-converter and amplifier, or down-convertamplifier 30 is shown and includes a Digital Down-Converter (DDC).Optionally, a mixer and an intermediate frequency (IF) device, or modulecan be used. A transmit up-convert amplifier 40 is implemented using aDirect Digital Synthesizer (DDS). Optionally, a mixer and IF device, ormodule can be used. A special FFT processor 50 is configured to slicethe input based upon knowing the periodic nature of the wave forselective sampling. A complex sinusoidal signal generator 60 implementsone of the four sets of equations shown below with reference to FIG. 2in order to transmit a signal over a wave. A symbol creation module 70is configured to break the symbol into a Wobble that transmits thedigital information. A symbol processing module 80 is configured tomerge the Wobble decode from the plurality of special FFT processors 50to find consensus on the symbol. Consensus is found in analyzing theresults from the FFT results from each of the two peaks for each antennafor the wobble. For the complex CTwists wave, six votes are delivered tothe decision maker. At least two votes need to agree on a wobble valuewithout an equal counter opinion. The strongest opinion will be usedunless there is a tie. A tie is indicated as an error. An outbound blockprocessing module 90 is configured to break outbound data into sets ofForward Error Recovery blocks and feed those blocks symbol by symbol tothe symbol creation module 70. In operation, an inbound block processingmodule 95 is configured to receive symbols from the symbol processingmodule 80, assemble these symbols into blocks, process these blocksthrough forward error recovery, and process the resolved data.

According to one construction, circulator 20 is a Saisum dual junctioncoaxial circulator, Part No. SS-HCC5628A available from Saisum, F/15,ITC Building, Southlake Road, Luohu District, Shenzhen, China.Optionally, other known constructions can be used.

In contrast, eSpin created its wave through antennas with polarizationdiversity driven by the same signal with phase delays produced throughcoax delay lines and received its wave back through the coax delay lines(de-spinning the signal). This caused the distinct signals to be mergedtogether. However, problems still exist with implementation.

CTwists directly drives the antennas 12, 14, and 16 of antenna array 10(see FIG. 1) with polarization diversity with its signal (giving a widerrange of phase adjustment) and receives and processes the signals fromeach antenna without the loss of any information. Since CTwists wavesare created using sinusoidal functions, they can be processed throughfast fourier transforms (FFTs) in order to ascertain information aboutthe CTwist waves, such as we identify the peak frequencies, we get thepeak amplitudes, and we get the phase.

CTwists promises a more efficient use of presently available radiofrequencies. The demand for the radio frequency spectrum is growingrapidly and CTwists can help meet that need.

The CTwists wave has been produced in experiments using crossed dipoles.The experiments generated and received the CTwists wave without dataencoding. The experimental results have been reproduced in simulationswhich have refined the CTwists approach.

The CTwists wave creates two peaks in a frequency spectrum. The peaksare at the carrier frequency minus the twist frequency and the carrierfrequency plus the twist frequency. Each peak was observed to beultra-narrow-band. When the peaks are suppressed, the space between thepeaks is shown to have no energy. The formulas used to create CTwistswaves and Circular waves can be seen in FIG. 2:

Where: f_(c)—is the carrier frequency

-   -   t—is the time    -   θ—is the carrier phase angle    -   f_(t)—is the twist frequency    -   λ—is the twist phase angle

A. CTwists Simple Wave

An end view of the CTwists wave can be seen in FIG. 3. The ratio of thecarrier frequency to the twist frequency determines the number of lobes,or petals 110 in the flower-like-picture of the CTwists wave, taken inend view. The CTwists wave is depicted as a thread 108. Thegeometrically defined thread segment 110 of thread 108 represents thecarrier that CTwists uses for data transmission. FIG. 4 shows the sideview of the wave 108 with thread segment 110. Note: only enough of thewave is shown to define the pattern which is repeated. FIG. 5 shows atop view of the wave 108 and thread segment 110. FIG. 6 shows a 3D viewof the wave 108 and thread segment 110.

Each antenna is processed separately upon reception using a Fast FourierTransform (FFT) algorithm which processes the samples from the timedomain and creates a frequency domain view of the wave. A sample FFT canbe seen in FIG. 7. Peak 210 shows the ultra-narrow band line created atthe carrier frequency minus the twist frequency. Peak 220 shows wherethe carrier frequency would be seen had it not disappeared. Peak 230shows the ultra-narrow band line created at the carrier frequency plusthe twist frequency.

The CTwists wave can be created using a crossed dipole antenna system asseen in FIG. 8. A transmitting antenna 310 and a receiving antenna 320are shown spaced from one another in a wireless configuration fortransmitting and receiving there between a digitally encoded CTwistswave, or thread(s). Note: this antenna system can be used to createcircular polarized waves as well. In both instances, a right handed waveis created in one direction orthogonal to the transmitting antenna and aleft handed wave is created orthogonal to the transmitting antenna inthe opposite direction, superposed over the right hand wave.

For CTwists, two communication threads are created; namely, one righthanded and one left handed. Half of the power is wasted unless areflector is placed behind the transmit antenna to redirect the wastedpower.

The CTwists wave has multiple unique characteristics. First, a reflectedwave does not create a continuous null spot for reception. Secondly,waves penetrate obstacles more effectively than horizontal, vertical, orcircularly polarized waves. Third, waves penetrate the ionosphere moreeffectively when ionosphere is disrupted by sun spots, coronal massejections, or scintillation than horizontal, vertical, or circularlypolarized waves. Finally, the wave can, on reception, be recognized attwo different frequencies on each of the antennas with polarizationdiversity. This provides redundancy and the ability to distinguish theCTwists wave from different types of interference.

According to this implementation, the two orthogonal antenna systems forCTwists produce the simple CTwists wave.

B. CTwists Complex Wave

More complex CTwists waves are produced using three orthogonal antennas.FIG. 9 shows the simplest of three different orthogonal antenna systemsin the form of three crossed dipoles. Antenna 410 represents the X axis,antenna 420 represents the Y axis and antenna 430 represents the Z axis.As a result, antennas 410, 420, and 430 provide an orthogonal array ofcrossed dipole antennas, similar to antenna array 10 of FIG. 1. Note:the X, Y, and Z antennas transmit and receive along an axis (shown asaxis 440) which is equidistance from each of the X, Y, and Z axes whichis an angle of approximately 54.74% between the X, Y, and Z axis andrepresents a potential loss of approximately 42%. However, due to thenature of the wave extending along this new axis, it is projected to beless. FIG. 10 shows an end view of this wave, or thread 508 and a threadsegment, or lobe 510 of the communication thread is identified. FIG. 11shows the front view of the wave 508 and thread segment 510. FIG. 12shows the top view of the wave 508 and thread segment 510. Finally, FIG.13 shows the 3D view of the wave 508 and thread segment 510. Note: dueto dimensional limitations, the activity in the direction oftransmission and reception was processed as a projection.

Based on limited early testing, the 3D threads which communicate theCTwists data are believed to be much less interfering than traditionalwaves and much more penetrating through obstacles. The past 30 to 42 dBimprovements of selectivity of signal out of noise were not expected byprior investigators. The present CTwists wave generation and receptionvia specific antenna arrays unexpectedly solved problems previouslyencountered and the antenna configuration provided significant advantageusing the three orthogonal antennas rather than the prior eSpin threeantennas separated by 120 degrees within a plane. Such realization ofimprovement would prove to be a surprise to those of ordinary skill inthe art.

FIG. 14, FIG. 15, FIG. 16, and FIG. 17 are respectively end, front, top,and 3D perspective views of a Super Circular wave, or thread 608produced by three orthogonal antennas in an antenna array.

There are two types of the three orthogonal antenna systems. First,there are omni-directional three orthogonal antenna systems. Second,there are directional three orthogonal antenna systems.

The three crossed dipole antenna system is the simplest of theomni-directional three orthogonal antenna systems. However, by using thethree-dimensional edge of cell phones, tablets, or laptops for the Zcomponent, these can also be included into the omni-directional threeorthogonal antenna systems. Multiple communication threads of differenttypes emanate in all directions from these antennas. Note: theseantennas can also produce what is termed “Super Circular Polarized”waves, in that, depending upon the direction the communication threads,they are either circular or elliptical and either right-handed orleft-handed based upon the contributions of each antenna in thatparticular direction. Circular polarization is one instance ofelliptical polarization.

Directional three orthogonal antenna systems include a horn and aparabolic directional three orthogonal antenna array. More particularly,FIGS. 18A and 18B illustrate an antenna array 710 including a horn 718housing three orthogonal antennas 712, 714, and 716 which will producemultiple communication threads with the majority of the energy focusedin a 60° wedge with an approximate 12 dB gain.

The three antenna complex antenna array 710 of FIGS. 18A and 18Bcontains three ¼ wave antennas 712, 714, and 716 each with ¼ wavecircular radial bases 722, 724, and 726. Antennas 712, 714, and 716point toward the opening of the horn, or horn antenna 718. Communicationthreads are created based upon the interactions of the three ¼ waveantennas 712, 714, and 716, and from the interactions of the three ¼wave circular radial bases 722, 724, and 726. Optionally, the complexarray 729 of three antennas 712, 714, and 716 (from FIG. 18A) whenplaced at the focal point of a parabolic reflector, such as parabolicreflector 728 of FIG. 18C, focused inward produces an optional parabolicthree orthogonal antenna system over that depicted by antenna array 710of FIGS. 18A and 18B. Both the ¼ wave antennas 712, 714, and 716 and ¼wave circular radial bases 722, 724, and 726 are tuned so that theirelectrical length and size resonates in the middle of the target radiofrequency spectrum and adjusted position wise to minimize return loss(i.e. a Standing Wave Ratio (SWR) of 1 to 1). The parabolic threeorthogonal antenna system of antenna array 710 produces a narrow beamwith a high gain in excess of 18 dB.

C. Control

A key to the CTwists processing is the direct control of the antennasrather than delay lines, as was the case in eSpin. FIG. 19 illustratesan example simplified flow of data in this direct antenna controlprocess. An antenna transmitting and receiving process control system728 is illustrated. A plurality of individual mixers 730 each implementan intermediate frequency (IF) process via individual intermediatefrequency (IF) processors 753 that mixes a defined oscillator frequencyto up convert the frequency to a desired range for each respectiveantenna. Likewise, a plurality of individual mixers 750 implement anintermediate frequency process via intermediate frequency (IF)processors 754 that mixes a defined oscillator frequency to down convertthe received frequency to a desired range. The IF amplifiers and filtersof IF processors 753 and 754 are important to this effort in bothtransmit for up convert and reception where down convert brings thefrequency down to a range that can be processed.

Individual antennas (not shown) are attached to circulators 740 in FIG.19. Note: the 2 position of each circular is attached directly throughconnectors and coax to an antenna (such as the antennas of FIGS. 18A-C).The circulators attach to low noise (LN) amplifiers 752, mixers 750, IFamplifiers and filters 754 for received signals (3 position), and to IFamplifiers and filters 753 from mixer 730 for transmit (1 position). Thedigital to analog converter (DAC) 756 feeds signals to mixers 730 andthe analog to digital conversion (ADC) 760 receives signals from IFamplifiers and filters 754. Note: the frequency of the feed from thelocal oscillator 758 to the transmit mixers 730 may be different fromthe feed from the local oscillator 759 to the receive mixers 750. Analternative to the analog up-convert/down-convert approach shown in FIG.19 is to employ a digital down-convert (DDC) and direct digitalsynthesizer (DDS) approach.

As shown in FIG. 19, system 728 also includes a secure EEPROM 776 thatcontains FPGA programming and a Linux operating system forinitialization. EEPROM 776 is maintained with a current level offunctional programming. EEPROM 776 is isolated in order to preventcorruption from any source. A SIM card 782 is configured to provide SIMfunction that saves unique data for the device of system 728 along withthese configuration parameters; namely, server frequencies, uplinkfrequencies, and twist frequencies. For each client and server, the MACaddresses, encryption certificates, and the appropriate combinations ofthe configuration frequencies will be encoded upon the SIM card 782 SIMcard 782 communicates bi-directionally through a universal asynchronousreceiver/transmitter (UART) 778 with a development PC board 762containing a pair of Field Programmable Gate Arrays (FPGAs) 763 and 765.Optionally, PC board 762 and FPGAs 763 and 765 can be implemented on anASIC.

As shown in FIG. 19, each FPGA 763 and 765 includes a respectivetransmitter 790 and receiver 792, having transmitting and receivingcircuitry. Each FPGA 763 and 765 includes a Xilinx Zynq-7000 allprogrammable system of a chip (SoC), as well as resident Linux operatingsystems 772 and 774. Additionally, each FPGA 763 and 765 includesrespective processing circuitry 797 and 795, as well as memory 794 and794.

A Gigabit Ethernet interface 780 shown in FIG. 19 allows for data to bereceived into or transmitted from the CTwists communication system.Accordingly, Gigabit Ethernet connection 780 is provided to PC board 762for network connectivity with other devices and systems.

II. Ultra-Narrow Band Communication

CTwists ultra-narrow band communication promises a more efficient use ofthe available radio frequencies. Demand for the radio frequency spectrumis growing rapidly and CTwists ultra-narrow band communication can helpmeet that need.

The objective is to directly encode digital information onto anultra-narrow band wave without producing side bands and becoming wideband. This should allow many more communication channels and reduce thepower required to transmit a given amount of data. As with GFSK andGMSK, CTwists ultra-narrow band communication smooths the transitionbetween frequencies. CTwists ultra-narrow band communication uses veryclose frequencies—closer than GMSK. However, rather than introducingintermediate frequency steps, as does GFSK and GMSK, CTwistsultra-narrow band communication produces a transition in which the poweris maintained at the same level as the signal changes from one frequencyto another, reducing power at one frequency in conjunction withincreasing power by the same amount in the other frequency. This is doneover a transition period designed to not produce side bands.

A. The Wobble

Information is transmitted in symbols. The time to communicate a symbolis termed a “Wobble”. The Wobble time is connected to a certain numberof twists for CTwists communication threads or a number of carrierfrequency cycles for horizontal, vertical, or circularly polarizedcommunication. The Wobble is a tunable parameter. For purposes of thefollowing examples, the number 32 twist for CTwists waves and 32 averagecycles of the band segment for all other waves is used. However, thisvalue can be tuned to maximize performance and minimize error rate. FIG.20 shows a communication containing 5 Wobbles. A base referencefrequency 810 is shown relative to a smooth transition period 820. EveryWobble starts at this frequency. The duration of the base frequencytransmission is ½ the duration of the Wobble. At the end of the basefrequency, a smooth transition period is used to avoid the production ofside bands. The smooth transition period is shown as dashed rectangles.After the first smooth transition period in the Wobble, the data signalcontinues for ½ of the Wobble time. At the end of the data signalperiod, another smooth transaction period occurs to bring the frequencyback to the base frequency as can be seen in section 820.

In this example, the data levels are determined by frequency incrementsabove or below the base frequency. The frequency delta is a tunableparameter as is the number of levels. In this example, the 5 frequencylevels encode data as follows:

TABLE 2 Level Value Assignment Level Assigned Value +2 3 +1 2 Base null−1 1 −2 0

In this example, the amount of data encoding by frequency level is 2bits per symbol. The base level also provides a reference point for thephase of the Wobble. The phase of the base defines zero. Using smoothtransitions the phase of the data signal can be set to a specific valueto encode more data per Wobble. Of the 360 degrees of possible values,from 16 to 64 possible target settings for phase would yield from 4 to 6bits additional information per symbol. Again the phase angle targets,associated values, and the error tolerance are tunable values.

In this example, the total amount of data encoded in a Wobble or symbolranges from 6 bits to 8 bits.

B. Smooth Transition

Key to the goal of not producing side bands and staying ultra-narrowband is the smooth transition. The amount of the Wobble dedicated to thetwo smooth transitions is also a tunable parameter. For this example,each smooth transition is assigned ¼ of the base or data signal. Withinthe smooth transition period, the time to start the transition isdetermined by considerations from the current and target phase. Thetransition starts at the phase beginning of the target phase. At thatpoint, the power of the current frequency is lowered in conjunction withthe increase of the power from zero of the target frequency.

The total power on the two frequencies can be calculated based upon thesquare root of the sum of the squares of the E-field strength for thetwo frequencies. This relationship can be seen in FIG. 21. As with theright triangle where the hypotenuse stays the same length as the lengthsof the two sides vary.

C. FFT Results

Each Wobble on reception is processed using a Fast Fourier Transform(FFT). FIG. 22 shows the typical result for a CTwists simple or complexwave. Note: for other waves, only the peaks in section 910 are seen. Thepeaks in section 920 are unique to CTwists waves. In every FFT, the linefor the base should appear. The other line determines the data linevalue. The distance from the base line and direction indicates the first2 bits of the data value. By processing the associated real andimaginary values with each line with the arc tangent function, the phaseof the wave represented by the line can be determined. By treating thephase of the base line as phase zero and then evaluating the phase ofthe second line, the value encoded in the phase of the data line can beevaluated—the additional 4 to 6 bits. With the CTwists wave, the secondset of peaks provides a redundant check. Each additional antenna shouldprovide checks of the data value.

Errors can be detected when phase angles are out of range which may becorrected if other peaks offer better results. When different sets ofpeaks offer different results, an error is reported if the vote of thepeak sets is a tie. Otherwise the majority wins.

III. Special FFT Processing

The Fast Fourier Transform (FFT) algorithm is controlled by severalparameters:

-   n—the power of 2 that determines FFT Size (in this case 16)-   FFTsize—The size of the FFT and the optimal number of samples (in    this case 65,536)-   NBins—The number of bins=FFTsize/2 (in this case 32,768), Each bin    contains two floating point numbers—real & complex.-   SR—The sample frequency-   Fmax—The maximum frequency tracked by the FFT=SR/2-   FR—The Frequency Resolution=Fmax/NBins

The trade-offs of the FFT algorithm are as follows. First, the samplefrequency (SR) determines the amount of time needed to collect thesamples. The time for samples=SR*FFTsize which for a SR of 67,108,864the time required is 0.00195313 seconds. Secondly, the frequencyresolution (FR) is dependent on the sample frequency (SR) such that thehigher the sample frequency—the lower the frequency resolution. In thiscase, the FR=1,024.

The nature of the Wobble, in its periodicity, allows clean periodicsampling where either every other Wobble can be sampled for twice thetime to determine timing for the receive window or, once the timing ofthe Wobble is determined, the Wobble sample can be repeated the 256times to complete the optimal number of samples for the algorithm.Padding with zeros causes loss of frequency resolution, but properlyknitting together the periodic Wobble samples will maintain thefrequency resolution of the bins.

A. Wobble Skew Determination

The server will transmit two periodic signals with the second ⅝ths of aWobble out of phase from the first ⅝ths of a wobble. In FIG. 23, everyother Wobble is sampled and the resulting FFT can be processed todetermine the skew of the time of the Wobble sample as compared with thetrue begin of the Wobble. FIG. 24 shows a FFT of the results of the outof phase every other Wobble sample. Peaks 1010 show the lower broadcastfrequency that has three peaks which can be used to calculate the Skew(how far out of phase) the sampling windows are from the actual Wobblestart.

FIG. 25 shows an adjusted sampling time start that shows a Skew of 0. InFIG. 26, both of the broadcasts have only two lines in their peaks.Peaks 1020 are now only two peaks for the lower broadcast while theupper broadcast frequency stays at only two peaks.

B. Wobble Decoding

Note: a Skew of 0 to ⅜ths of a wobble produces good results for Wobblesampling. Once the sampling start time window is adjusted so that theSkew is within the range of 0 to ⅜, the Wobbles can be sampled withinthe window and repeated 256 times and fed to the FFT algorithm todetermine the Symbol in the Wobble. A queue of Wobble FFT decoding willbe created. Enough FFT resources need to be available to keep up withthe Wobble decoding.

IV. Communication Management

CTwists Communication Management promises a more efficient use of theavailable radio frequencies. The demand for the radio frequency spectrumis growing rapidly and CTwists Communication Management can help meetthat need with networks that provide consistent reliable secure service.CTwists Communication Management provides for the proper usage of thesenew resources.

The initial target implementation for CTwists is to demonstrate itscapabilities in the 2.4 GHz band. FIG. 27 shows the non-overlappingchannels in that Wi-Fi band. Channel 1030 shows channel 1 in that band.It is a 22 MHz channel that will support 54 Megabits per second of datarate. Its range is about 35 meters.

Because CTwists up converts the signals produced with its FPGAs andDACs, the actual target frequency is adjustable. In this example, ontransmit, the frequencies produced by the FPGAs and DACs are in therange of 2 to 26 MHz. These are then up converted to the 2.4 GHz rangewhile maintaining phase.

On reception, the 2.4 GHz range frequencies are down converted to the 2to 26 MHz range and then processed through the ADCs and FPGAs whilemaintaining phase. On reception, the Wobbles are processed separately,which means the number of samples are less than the target number, butthe FFT result will be extrapolated by repeating the Wobble 256 times.

The initial implementation of the system will be based upon FPGA whichhave sampling rate limitations and FFT hardware constraints. Samplingrates should be under 130 MHz and the “n” for the FFT should be 16 orless. There are many options, but FIG. 28 illustrates two of them;namely, options 1 through 3 for CTwists and Super Circular.

Three nested options can be used for the CTwists wave. In option 1between the high peaks and the low peaks, there is sufficient room tofit option 2 and between the high and low peaks of option 2 there isroom for option 3. This is done by adjusting the local oscillator to upconvert and down convert the options to different frequency ranges.Note: these options fit into approximately the same frequency space asone 802.11 channel that can carry 54 Mbps. This relates to 51 times moreaggregated channels with same data capability, 53 times as much datacapability, and with a 17 dB gain which means it requires 50 times lesspower for the same distance.

The option 1 channels could be used for server to client communication;the option 2 channels could be used for client to server communication;and the option 3 channels could be used to request service from serverand clients with very low data uplink requirements. CTwists' options 1through 3 can be seen in FIG. 29 where channels 1040 point to the option3 area and options 1 and 2 are indicated by O1 and O2.

The Super Circular option has half the redundancy and may interfere morewith legacy waves, but, as compared with 802.11n channel 1, it has 180times the number of channels aggregated to the same data rate, 193 timesas much data capability, and with a 23 dB gain which means it requires200 times less power for the same distance.

In practice, the Super Circular data range would be split with one rangefor server to client communication and one range for client to servercommunication. Note: for Super Circular communication, the Twistfrequency is the average frequency of the range.

CTwists wave will be evaluated against the Super Circular wave. Thereare two major factors; namely, dB gain of each wave, and legacy waveinterference.

A. Server Channel Management

In either the CTwists wave or the Super Circular wave environment, manymore channels are available to manage. The channels are smaller and ifthe upload or download requirement of the client is not met by onechannel, then they can be aggregated to provide sufficient capability.The approach to managing this vastly increased number of channels shouldbe rethought in order to take full advantage of the opportunity toimprove both frequency spectrum utilization and client service level.

B. Spectrum Management

The server is in a unique position to handle multiple tasks. First, theserver can monitor noise levels experienced in each channel. Second, theserver can monitor error rates in each channel. Third, the server canmonitor client data requirements. Fourth, the server can allocate lownoise and low error rate channels first. Finally, the server candynamically adjust data channel aggregation and redundancy to meetclient needs.

C. Noise Level Management

The server can monitor the spectrum connected with its channels andtrack periodic interference and random interference in the channels.This is an ongoing activity and provides the current and historical dataneeded to make optimal channel allocation decisions based upon noiselevel history and level.

D. Error Rate Management

The server can track channel error rates for data server bound andclients should report their error experience for channels on which theyreceive data from the server.

E. Error Recovery

In FIG. 30, the data flow from transmit to receive is illustrated. Onthe transmit side, based upon the error experience for the set of datachannels 1136 being used and the data rate requirements of the client, aset of frames is created to be transmitted in parallel prepared forForward Error Recovery. The plan is to use our dynamic Reed-Solomonerror correcting code, such that, the amount of redundancy is adjustedappropriately based upon the error history. The Tx Data Block Processor1130 takes an outbound data block and breaks it into Reed-Solomon framesto be transmitted in parallel. In a symbol generation module 1134, theframes are serially broken into symbols and transmitted over theparallel data channels 1136 which shows seven different data channelsbeing transmitted over the three antenna array at different frequencies.The seven data channels receive activities from an FFT processing module1138 that processes the symbols in parallel communicated on differentfrequencies (different channels) and use the symbols to re-build theframes to be processed by the Reed-Solomon function in the Rx Data Block1132 which rebuilds the original data block. Note: error recovery isdone at two levels 1) as each symbol is received the six different FFTresults for complex CTwists symbol values are processed and theconsensus determines the value returned; 2) at the Reed-Solomon levelframe errors are detected and corrected. For super circular waves, onlythree FFT symbol results are available to determine a consensus. If noconsensus is found, then a symbol error has occurred. The communicationchannel 1120 is where the frames flow to the Reed-Solomon errorcorrecting code if too many errors are experienced, then an error isreported out of this level. Note: other Forward Error Recoverytechnologies other than Reed-Solomon are available and the same dynamicnature can be added to them.

F. Client Channel Management

One approach, as stated earlier, is for the server to broadcast twospecial cyclical broadcast channels with the wobble phasing, such that,the bottom wobble broadcast lags the top wobble broadcast by five eightsof a wobble as seen in FIG. 25. This allows the client to listen to thebroadcasts for twice the 256 wobbles that represents a complete samplefor every other wobble. By sampling every other wobble, the client willbe able to process the FFT to determine the Skew of the sampling windowand to adjust that Skew to be three sixteenth of a wobble. With thesampling window set at this value, variations due to client's movementcan be evaluated by the calculated Skew drift over 256 of the standardsampling set of 256 wobbles. Note: the time for a wobble is set by theserver's atomic clock (like the Microsemi CSAC SA.45s Chip Scale AtomicClock) and is not effected by Doppler. As long as the client is movingless than 1900 miles per hour, the Skew drift will be less than thetarget Skew of three sixteenth as shown in FIG. 31. The Skew drift isone measure of the client's motion. Note: within the Skew window of aSkew of zero to a Skew of three eights, the client can receive dataproperly. After the 256 sets of 256 wobbles (one fourth of a second) atdigital finite impulse response (FIR) filter can accurately measure theapparent frequency (f′) of the center of the top signal beingbroadcasted by the server. For stationary clients, the client's clock issimply synchronized with the server's clock. For mobile clients, thisinformation along with the known server frequency (f) and the knownspeed of light (c), the client velocity relative to the server (v) canbe calculated:v=c*(1−(f/f′))with this value a double check of the client velocity can be done withthe measured Skew drift. These two calculations will allow for minorclock adjustments to the client's clock if is not yet stepping with theserver's clock. The client's clock will be maintained with a PhasedLocked Loop (PLL). Since the servers are synchronized with each other,once a client's clock is stepping with one server, then clock adjustmentshould not be required. When the client communicates with the server,the client's frequency must be adjusted by a factor calculated from theclient's velocity vector relative to the server. Also the timing of theclient transmissions are to be timed, such that, the server's samplinginterval is properly met. Client service requests are submitted to theserver on one of the designated server request line frequencies chosenthrough a hashing algorithm based upon the client's information.

The server response frequency is then monitored for a response. Therequest transmits credentials from the client for authorized usagevalidation and connection speed requests. The server response assignsthe set of download and upload frequencies.

The client will receive data from the server on a shared channel andonly process data addressed to the client and would only be able todecrypt data addressed to the client. The channel dedicated for clientto server communication will remain open for durations needed by theclient. The client to server channel reacquisition time requires a turnaround with the server which encourages the maintaining of that channeluntil client to server communication goes relatively silent.

G. Multi-Server

In Multi-Server configurations, the servers coordinate severaloperations. First, the servers coordinate their clocks—steppingtogether. Second, the servers coordinate Client Communication—providingredundant communication with the client. Third, the servers coordinateClient Encryption—using shared keys for encrypting client data. Finally,the servers coordinate Security Channels—for encryption keys andidentity information.

The data is kept in synchronization within gossip groups consisting ofthe client and the servers servicing the client. Through gossip what isknown by one member becomes known by all. This ensures redundant securecommunication. In multi-server implementations, the client connects withthe two best servers for communication and uses three or more serverclock broadcasts to determine (as it would with GPS) its location,speed, and acceleration. These servers will provide the needed data tocreate a highly accurate map for use with autonomous vehicles(self-driving cars) along with the needed reliable and securecommunication.

H. Ultra Narrow Band Advantage

For the 2 GHz to 7 GHz frequency range the formula for required poweris:P _(dbm)=−165+10*log₁₀(bandwidth)This represents a 17 dB reduction in power for a 200 Hz signal ascompared to a 10 KHz signal and a 50 dB reduction in power for a 200 Hzsignal as compared to a 20 MHz signal. Note: this is the 17 and 23 dBadvantage calculated in the Power dB row of FIG. 28.

I. Clock Synchronization

The servers' clock will be driven by an atomic clock. A potential clockis the Microsemi CSAC SA.45s atomic clock. The servers will synchronizetheir clocks and step together.

The client will synchronize its clock with the server in one of twoways. First, for the stationary client a long term finite impulseresponse (FIR) filter on the center broadcast frequency (a knownfrequency) can be used to set the client's clock. Second, for a clientwith motion, two factors must be captured; namely, the value determinedby a long term FIR for the center broadcast frequency which is affectedby Doppler, and the exact time difference between two measurements todetermine Skew separated by 256 wobbles repeated 256 times (the wobbleis a known quantity not affected by Doppler). The second value is usedto set the client's clock in conjunction with the Doppler adjustmentdetermined by the first value.

V. Substance Detection and Manipulation

The CTwists waves, both the complex and the Super Circular, provide anopportunity to much more effectively use radio frequency substancedetection. The complex CTwists wave penetrates much more effectivelythan conventional radio waves and delivers two different quantums ofenergy in the form of coupled photons of differing frequencies. Thesetend to be adsorbed together. The radio frequency range used in thisapproach has so many adsorption lines that it has been, in the pastconsidered black body radiation (and any frequency adsorbed and anyradiation out). Motion stops at absolute zero and increases withtemperature. However, even at these low energy levels, everything isquantized. The CTwists Substance Detection and Manipulation depends uponthe unique nature of the complex CTwists wave to 1) penetrate muchbetter than normal radio waves and 2) to adsorb in a paired energyconfiguration. This unique pairing of frequencies and energy levelsmakes possible CTwists spectroscopic analysis.

A very important advantage is provided because the energy in this rangeis non-ionizing which means it does not cause physical harm. This is incontrast to ionizing radiation which can cause cancer or other ailments.

The approach is to use automated equipment to broadcast waves to excitea substance using Super Circular waves at different frequencies and waitand detect the radio wave emitted upon relaxation.

A. Initial Substance Scanner

The purpose of this device is to methodically try to excite a substancewith a range of radio frequencies using the Super Circular wave whilemonitoring for radio wave responses from the relaxation of the substancethat matches the exciting wave. We are limiting the substance initialfingerprint to measurements where the frequency in (the energy of thephoton) matches the energy out—the relaxation frequency matches theexcitation frequency (the energy of the photon). FIG. 32 shows thisscenario. Note: the waves in these figures are exemplary and notreflective of the actual waves. More particularly, an excitation wave1210 is depicted. A change in energy level between an initial energylevel 1220 and an excited energy level 1230 is next shown. An emittedwave 1240 is further depicted after relaxation. In doing so, the initialfingerprint of the substance is produced. The scanning activity shouldbe done in an anechoic chamber with a Faraday cage to avoid backgroundinterference. Only the instances where the received wave's frequency, asseen in the FFT, matches the transmitted wave frequency are added to thefingerprint.

Once the first pass is done, using the response frequencies, complexCTwists waves are then tried by creating designer waves which useCTwists complex waves with their two peaks configured to match two ofthe frequencies cataloged in the first pass. When exciting with thedesigner wave, results are monitored for a relaxation signal whose FFTpeaks map to pairs of these frequencies. FIG. 33 shows the use of adesigner wave 1310, both at unexcited and excited levels of energy, usedto excite the target substance from energy level 1320 to energy level1330 with a photon pair of the designer wave. After relaxation, if thematching pair (correct FFT peaks) of photons is emitted from the emittedwave 1340, then the combination is a valid designer wave and is added tothe fingerprint for the target object.

Once the designer waves that produce a complex response are determined,then additional scans will be done while designer waves of excitationfrequencies are present. This will find higher excitation levels thatcan only be reached when the lower designer wave of excitation ispresent. FIG. 34 shows the use of a designer wave 1410 to excite asubstance to a higher excitation level 1450 while testing that level fornew excitation frequencies at that higher energy level 1430 above thebase energy level 1420. These higher excitation levels will be added tothe substance's fingerprint, if the resulting wave 1460 matches (or hasthe same FFT line) as the query wave 1440.

Once the single frequencies are mapped above the excited level, thenpairs of these waves can be tested as potential second level designerwaves. FIG. 35 shows the testing of potential second level designerwaves. The excited level is maintained using designer wave 1510 whichmoves the energy level from 1520 to 1530. The wave pair 1540 is a secondlevel designer wave candidate. If there is a resultant wave pair 1560and the FFT lines match the expected frequencies as the relaxation ofthe higher excitation level 1550 occurs, then a second level designerwave has been found.

If necessary, this process can be done to additional levels.

The goal is to develop a fingerprint that is unique to the substance, sothat, when the designer waves in the fingerprint are sent, only thetarget substance responds in a manner that matches the fingerprint.

B. Analysis Through Quantum Computational Chemistry

Where the substance's exact chemical composition is known, models can beused to predict the exact frequencies that would excite the substanceand where designer waves would cause an excitement that would emit adesigner wave response.

The secondary excitement levels can also be calculated. Note: thesimulations are dependent on the type of solution in which the substanceis suspended.

C. Substance Scanning and Detection Systems

Substance detection has many applications from entry portals to landmine detection, to cancer scanning, to contraband detection, and manymore.

D. Portal Device

FIGS. 36A and 36B show one conceptual exemplary portal device 1608 whichcan be programmed to detect a wide range of substances. An array oftransmitters 1610 are configured within device 1608 to excite a targetsubstance, or object 1612 and upon relaxation, the receiving devices1620 hear the signal if the substance is present. Note: for diagramsimplification, only one receiving device 1620 is numbered. However, theportal device 1608 is surrounded by receivers 1620 on both sides of theencasement, or housing 1609, as well as on the top and bottom surfaces.A more detailed description of these antennas can be seen in FIGS. 38Aand 38B and the control box 1630 can be seen in FIG. 19. Note: thecontrol lines 1640 connect all the transmitters 1610 and receivers 1620surrounding the portal to a system controller 1630 which is an array ofcontrol elements similar to system 708 of FIG. 19. One such system isprovided for each transmitter, as well as each receiver.

E. Initial Scanning Chamber

FIG. 37 shows a portal device 1608 containing an initial scanningchamber 1650, showing the placement of a target substance, or objectthat needs to be scanned. An array of transmitting antennas 1610 andreceiving antennas 1620 are provided about device 1608, although only asingle transmitting antenna 1610 and receiving antenna 1620 is shown forpurposes of simplification. The receiving antennas 1620 cover the sidewalls, as well as the top, and the bottom of the walls forming device1608. The control lines 1640 connect all the transmitters 1610 andreceivers 1620 surrounding the chamber to the control system module 1630which is an array of control elements similar to an antenna transmittingand receiving process control system 728 of FIG. 19. One system 728 isprovided for each transmitter, as well as each receiver.

F. Transmit and Receive Antennas

FIGS. 38A and 38B show a simplified drawing of one exemplary transmitand receive orthogonal antennas in an array 1640 for use with the portaland the initial scanning chamber of FIGS. 36A, 36B and 37, respectively,as a transmitting device 1610 and optionally a receiving device 1620.For a land mine detector, FIGS. 40A and 40B show an alternative roundantenna complex, as described below in greater detail.

G. Land Mine Detector

FIG. 39 shows a simplified exemplary diagram of a land mine detector1708. Land mine detector 1708 includes a control system module 1730,similar to module 1630, along with control lines, and a round antenna1720 described below in greater detail with reference to FIGS. 40A and40B.

FIGS. 40A and 40B illustrate a round antenna array 1720 that contains anorthogonal array of antennas, similar to array 1640 in FIG. 38B.

H. Substance Destruction

As with water molecules in a microwave oven, forced oscillations of asubstance can be achieved by transmitting at higher power for longerdurations at the determined designer frequencies as compared to whatdetection would require. Using this technique, a substance can be eitherbrought to a boil or caused to break apart.

It is understood that various applications can be made using theapparatus and method described above.

A digital information transmission apparatus can be provided having anantenna, a signal transmission medium, a transmitter, a digital signalgenerator, and a clock. The transmitter is coupled with the antenna andis configured to generate and transmit a continuous wave over thetransmission medium. The digital signal generator cooperates with thetransmitter and is configured to encode a digital configuration statechange to the continuous wave detectable at a receiving end as a digitaldata stream. The clock has a sampling frequency at least twice a Nyquistsampling frequency for the continuous wave coupled with the transmitterand the digital signal generator and is configured to synchronize timebetween the transmitter and a receiver.

A digital information transmission apparatus is provided having anantenna, a signal transmission medium, a transmitter, a digital signalgenerator, and a clock. The transmitter is coupled with the antenna andis configured to generate and transmit a continuous wave over thetransmission medium. The digital signal generator cooperates with thetransmitter and is configured to encode a digital configuration statechange to the continuous wave detectable at a receiving end as a digitaldata stream. The clock has an accuracy that supports at least twice aNyquist sampling frequency for the rate of change of digitalconfiguration state of the carrier frequency signal coupled with thetransmitter and the digital signal generator and is configured tosynchronize time between the transmitter and a receiver.

In compliance with the statute, the various embodiments have beendescribed in language more or less specific as to structural andmethodical features. It is to be understood, however, that the variousembodiments are not limited to the specific features shown anddescribed, since the means herein disclosed comprise disclosures ofputting the various embodiments into effect. The various embodimentsare, therefore, claimed in any of its forms or modifications within theproper scope of the appended claims appropriately interpreted inaccordance with the doctrine of equivalents.

What is claimed is:
 1. An apparatus for transmitting digital informationusing electromagnetic waves, comprising: an antenna having polarizationdiversity; and a signal generator coupled to the antenna, the signalgenerator configured to encode the digital information in the form of asymbol into the electromagnetic waves by using transitions within twomembers of a defined finite set of frequency/phase pairs of theelectromagnetic waves such that power stays constant during a transitionbetween a select two frequency/phase pairs within the set where choiceof a transition between the two members of the defined finite set offrequency/phase pairs determines the symbol.
 2. The apparatus of claim1, wherein a plurality of antennas are provided having polarizationdiversity between each pair of the antennas, each antenna paired with arespective signal generator.
 3. The apparatus of claim 2, wherein theelectromagnetic waves generate twisted waves.
 4. The apparatus of claim3, wherein the transition between the two members of the defined finiteset of frequency/phase pairs defines the symbol having a range of valuesfor the symbol that are a function of a level for the symbol.
 5. Theapparatus of claim 2, wherein a phase between antennas of afrequency/phase pair of antennas is used to determine twisted waveshapes and encode the phase portion of the frequency/phase pairs.
 6. Theapparatus of claim 1, wherein the transition between the two members ofthe defined finite set of frequency/phase pairs comprises a data symbol.7. The apparatus of claim 2, wherein the signal generators encode datausing a finite set of frequency/phase transitions between the pluralityof antennas.
 8. The apparatus of claim 1, wherein the signal generatorsmoothly transitions between the select two frequency/phase pairs. 9.The apparatus of claim 8, wherein phase adjustment is configured tomaintain power transition to realize constant power during thetransition.
 10. A data transmission apparatus, comprising: an antennahaving polarization diversity; and a signal generator coupled with theantenna, the signal generator configured to encode digital informationinto electromagnetic waves using transitions between two members of aset of frequency/phase pairs of the electromagnetic waves such thatpower maintains continuity during a transition between a select twofrequency/phase pairs within the set.
 11. The data transmissionapparatus of claim 10, wherein the signal generator maintains constantpower during the transition between the select two frequency/phase pairswithin the set.
 12. The data transmission apparatus of claim 11, whereinchoice of one transition between the two members determines a symbol.13. The data transmission apparatus of claim 10, wherein a plurality ofantennas are provided having polarization diversity between each pair ofthe antennas, each antenna paired with a respective signal generator.14. The data transmission apparatus of claim 13, wherein theelectromagnetic waves generate twisted waves.
 15. The data transmissionapparatus of claim 12, wherein the transition between the two members ofa select frequency/phase pair defines the symbol.
 16. The datatransmission apparatus of claim 13, wherein a phase between antennas ofa frequency/phase pair of antennas is used to encode the phase portionof the frequency/phase pairs.
 17. The data transmission apparatus ofclaim 13, wherein polarization diversity comprises each antenna of theplurality of antennas radiating in a uniquely different plane to realizeindependent phasing between each of the plurality of antennas thatproduces twisted waves.
 18. A method of transmitting data, comprising:providing an antenna having polarization diversity and a signalgenerator coupled with the antenna; using the antenna and the signalgenerator, generating a wave within a finite frequency/phase set; andencoding digital information in the form of a symbol onto the wave bysmoothly transitioning to another wave in the frequency/phase setthereby suppressing the creation of any non-filterable sidebandfrequency peaks.
 19. The method of claim 18, wherein the wave istransmitted in a single polarization.
 20. The method of claim 18,wherein the wave is transmitted as an elliptically polarized wave. 21.The method of claim 18, wherein the set of waves are twisted at a twistfrequency lower than the frequency of the finite frequency/phase set.